Adjustable power splitter and corresponding methods and apparatus

ABSTRACT

An adjustable power splitter includes: a power divider with an input and a first and second divider output; a first adjustable phase shifter and first adjustable attenuator series coupled to the first divider output and providing a first power output; and a second adjustable phase shifter and second adjustable attenuator series coupled to the second divider output and providing a second power output.

FIELD OF THE INVENTION

This invention relates to power or signal splitters in general and morespecifically to techniques and apparatus for adjustable power or signalsplitting or dividing.

BACKGROUND OF THE INVENTION

Power splitters or signal splitters or dividers are known. They areused, as the name suggests, to divide or split a signal into two or moreidentical signals. Identical or nearly identical signals can be used invarious systems where the same signal is processed in varying manners orthe same manner with more than one resultant signal being used in somecombination for some purpose. For example, if signals are subject to thesame interferences or distortions a practitioner can start withidentical signals and use differential processing and subtract theresultant signals to basically eliminate the common interferences. Asanother example, some amplifiers use or start with identical signals andprocess these signals in distinctly different manners and then combinethe resultant signals in some fashion to provide the final amplifiedsignal.

In many of these cases where identical signals are used to begin with,the relative phase of the resultant or resulting processed signals iscritical for a successful combination. Practitioners have used a phaseadjustment in one of the signal paths to attempt to address thisproblem.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying figures where like reference numerals refer toidentical or functionally similar elements throughout the separate viewsand which together with the detailed description below are incorporatedin and form part of the specification, serve to further illustratevarious embodiments and to explain various principles and advantages allin accordance with the present invention.

FIG. 1 depicts in a simplified and representative form an adjustablepower splitter being used in a Doherty power amplifier system inaccordance with one or more embodiments;

FIG. 2 in a representative form, shows a diagram of a power divider andfixed phase shifter in accordance with one or more embodiments, which issuitable for use in the FIG. 1 adjustable power splitter;

FIG. 3 depicts a representative diagram of an adjustable attenuator inaccordance with one or more embodiments;

FIG. 4 depicts a representative diagram of an adjustable phase shifterin accordance with one or more embodiments;

FIG. 5-8 show various performance data of one or more embodiments; and

FIG. 9 shows a flow chart of a method of adjusting a power split signalthat may be used in conjunction with the FIG. 1 system in accordancewith one or more embodiments.

DETAILED DESCRIPTION

Embodiments of the present disclosure concern adjustable power splittersand methods therein and uses thereof, e.g., adjustable radio frequencypower splitters, and more specifically techniques and apparatus forindependently adjusting the signals at each output of the adjustablepower splitter so the adjustable power splitter is or can be arrangedand constructed for use with a Doherty power amplifier. Moreparticularly various inventive concepts and principles embodied inmethods and apparatus corresponding to adjustable power splitterssuitable for use in amplifiers or Doherty amplifiers for improvedefficiency, etc. will be discussed and disclosed.

The instant disclosure is provided to further explain in an enablingfashion the best modes, at the time of the application, of making andusing various embodiments in accordance with the present invention. Thedisclosure is further offered to enhance an understanding andappreciation for the inventive principles and advantages thereof, ratherthan to limit in any manner the invention. The invention is definedsolely by the appended claims including any amendments made during thependency of this application and all equivalents of those claims asissued.

It is further understood that the use of relational terms, if any, suchas first and second, top and bottom, and the like are used solely todistinguish one from another entity or action without necessarilyrequiring or implying any actual such relationship or order between suchentities or actions.

In some embodiments much of the inventive functionality and many of theinventive principles are best implemented with or in integrated circuits(ICs) including possibly application specific ICs or ICs with integratedprocessing or control or other structures. It is expected that one ofordinary skill, notwithstanding possibly significant effort and manydesign choices motivated by, for example, available time, currenttechnology, and economic considerations, when guided by the concepts andprinciples disclosed herein will be readily capable of generating suchICs and structures with minimal experimentation. Therefore, in theinterest of brevity and minimization of any risk of obscuring theprinciples and concepts according to the present invention, furtherdiscussion of such structures and ICs, if any, will be limited to theessentials with respect to the principles and concepts of the variousembodiments.

Referring to FIG. 1, a simplified and representative high level diagramof an adjustable power splitter utilized, e.g., in a Doherty poweramplifier system in accordance with one or more embodiments will bebriefly discussed and described. In FIG. 1 as shown, an adjustable powersplitter 101 or radio frequency power splitter is coupled to or beingutilized with or driving an amplifier, specifically a Doherty amplifieror Doherty power amplifier 103.

The adjustable power splitter 101 includes a power divider 105 with aninput 107 and a first and second divider output 109, 111. The powerdivider 105 operates to divide or split a signal at the input 107 intotwo (or more in other embodiments—not specifically shown) signals, whichare identical or very nearly identical signals with in some embodimentsequal power. This equal power form of power divider is often referred toas a 3 dB divider since the resultant signals are each 3 dB less thanthe signal at the input. While the 3 dB divider is typical, otherdividers with multiple outputs or outputs with unequal signals could befashioned and used in some applications. One or more embodiments of thepower divider can be a lumped element circuit including an inductive anda capacitive reactance as will be further discussed below with referenceto FIG. 2

Further included in the adjustable power splitter 101, which in someembodiments is an adjustable radio frequency power splitter as shown inFIG. 1, is a first adjustable phase shifter 113 and in some embodimentsa first adjustable attenuator 115, which are series coupled to the firstdivider output 109 and configured for providing a first power output117. It will be appreciated that the adjustable phase shifter andadjustable attenuator can be series coupled to each other in any order,i.e., attenuator followed by phase shifter as shown or vice versa.Further included in the adjustable radio frequency power splitter 101 isa second adjustable phase shifter 119 and in some embodiments a secondadjustable attenuator 121, which are series coupled to the seconddivider output 111 and configured for providing a second power output123. As noted above, the order in which these are series coupled to eachother can be changed.

In various embodiments of the adjustable power splitter 101, the firstand typically the second adjustable phase shifter 113, 119 are eachdigitally controlled, e.g., by controller 125 and have a plurality ofstates. In one or more embodiments, the first adjustable phase shifter113 and often the second adjustable phase shifter 119, each have eightphase shifted states with each state providing a different amount ofphase shift. It will be appreciated that the first and second phaseshifter may have different phase shifted states, cover different ranges,and have different steps sizes, although typically they will beessentially the same. While digitally controlled, i.e., by changing oneor more control signals between differing discrete states or voltages(high or low, ON or OFF, level 1 or level 2, etc.), the adjustable phaseshifters in many embodiments are analog phase shifters. Thus in certainembodiments, the analog phase shifters, while analog are controlled toprovide a number of discrete phase shifts, i.e., digitally controlled,One or more embodiments of the adjustable phase shifters 113, 119 willbe discussed below with reference to FIG. 4.

In various embodiments of the adjustable power splitter 101, the firstand typically the second adjustable attenuator 115, 121 are eachdigitally controlled (one or more control signals change betweendiscrete steps or states and thus change between certain values ofattenuation), e.g., by controller 125 and have a plurality of states. Inone or more embodiments, the first adjustable attenuator 115 and oftenthe second adjustable attenuator 121, each have eight attenuation statesor attenuation levels. It will be appreciated that the first and secondattenuation may have different attenuation states, cover differentattenuation ranges, and have different attenuation steps sizes, althoughtypically they will be essentially the same. While digitally controlled,the adjustable attenuators in many embodiments are analog attenuators.One or more embodiments of the adjustable attenuators 115, 121 will bediscussed below with reference to FIG. 3.

Some embodiments of the adjustable power splitter 101 further include afixed phase shifter 127 that is configured for adding a fixed phaseshift between first and second signals at the, respective, first andsecond power outputs 117, 123. In some embodiments this can be a fixedand predetermined phase shift, e.g., 90 degrees, added to one signalpath, i.e., path between output 109 and power output 117 or path betweenoutput 111 and power output 123. In certain applications, e.g., Dohertyamplifier 103, a ninety degree phase shift is added to one path in theamplifier and the fixed phase shift can be used to offset this amplifierphase shift. The fixed phase shift in some embodiments is a phase shiftin a direction (negative or positive), e.g., a negative shift λ/8 129,such as a negative forty five degree shift, for the first signal at thefirst power output 117 and a phase shift in the opposite direction,e.g., a positive shift λ/8 131 such as a positive forty five degreephase shift for the second signal at the second power output 123. Usingthe forty five degree shifts gives a ninety degree phase shift betweenthe signals at the power outputs 117, 123. The phase shifter 127 ornegative shift 129 and positive shift 131 can be lumped element circuitshaving an inductive and a capacitive reactance as will be furtherdiscussed below with reference to FIG. 2.

As suggested above, the adjustable power splitter 101 typically furthercomprises the controller 125, which is configured and arranged tocontrol or for controlling the adjustable phase shifters and adjustableattenuators. The controller 125 in varying embodiments can be aprocessor or control circuitry or simply a one time programmable latch.The controller 125 can be provided data via an interface 133, such as aserial interface and in some embodiments this a serial peripheralinterface (SPI), which as is known typically includes a data in and out,clock signal, and chip select lines. Various approaches and variants orcombinations of those approaches can be utilized by the controller.Generally as will be explained below, control of the attenuators orphase shifters amounts to controlling switches, typically solid state orintegrated switches such as some form of field effect transistor switch.Thus the controller can be provided state information for all switchesin all attenuators and phase shifters and essentially act as one or morelatching buffers with outputs arranged and coupled to insure that allswitches are in the appropriate ON or OFF state. In some embodimentsthis can be as simple as fuses at each gate, which are set to insurethat all gates stay in a specified or desired state. Alternatively, thecontroller can be provided in essence an address or two or moreaddresses, which address(es) uniquely specify a state for eachattenuator and phase shifter. For example if all phase shifters andattenuators are 8 state devices a 3 bit address for each would uniquelyspecify the proper state and 4 such addresses could be provided to thecontroller, which would convert each address to the appropriate controlsignals for each attenuator and phase shifter and latch in these values,etc. In other embodiments the amount of phase shift and attenuation foreach of the four devices could be sent to the controller and it coulddetermine the proper state to realize the desired shifts andattenuations. The practitioner is free to choose from among these orother approaches or combinations to make and retain the appropriateadjustments to the adjustable attenuators and adjustable phase shifters.

In addition to the adjustable power splitter 101, the radio frequencyDoherty power amplifier 103 is shown where this amplifier includes amain amplifier 135 coupled via a matching network or circuit 137 to thefirst power output 117 and a peaking amplifier 139 coupled by itsmatching circuit 141 to the second power output 123. As will beappreciated by those of ordinary skill the main and peaking amplifiersare comprised of one or more stages of low level amplification andhigher power level amplification. The main and peaking amplifiers arecoupled via, respective, output matching circuits 143, 145 to a Dohertycombiner 147, which as is known is configured such that the mainamplifier provides the amplification for lower level signals and bothamplifiers combine to provide the amplification for high level signals.This is usually accomplished by, e.g., biasing the main amplifier, suchthat is operates in a class AB mode and biasing the peaking amplifiersuch that it operates in a class C mode. More complex embodiments arepossible where the adjustable power splitter has three outputs and theDoherty amplifier has a main and two peaking amplifiers with eachpeaking amplifier biased in different class C operating points. In oneor more of these manners, overall efficiency/linearity of the amplifiercan be improved over a wider range of signal levels. Adjustments to theadjustable attenuators and adjustable phase shifters can be made in anexperimental manner by monitoring power drawn by the peaking stage ormain stage or both as a function of signal levels and the like. Atcertain signal levels the peaking amplifier should begin to operate andamplitude and phase adjustments can be made with this in mind.

FIG. 1 illustrates additional features for the adjustable power splitterwith a Doherty amplifier where these features have been discussed aboveor will be discussed below in further detail. For example, the first andsecond adjustable phase shifters and the first and second adjustableattenuators are digitally controlled with each having multiple states,e.g., 8 or more or less states. The power divider can be a lumpedelement circuit including one or more inductive reactance and capacitivereactance and other elements. The lumped element circuit can furtherinclude a first lumped element phase shifter configured to provide anegative forty five degree phase shift for a first signal at the firstpower output and a second lumped element phase shifter configured toprovide a positive forty five degree phase shift for a second signal atthe second power output. As noted earlier the adjustable power splitterwith Doherty amplifier can also include or comprise a controller forcontrolling the adjustable phase shifters and adjustable attenuators.

Referring to FIG. 2, a representative diagram of a power divider andfixed phase shifter(s) in accordance with one or more embodiments, whichembodiments are suitable for use in the FIG. 1 adjustable powersplitter, will be briefly discussed and described. In FIG. 2 and allensuing FIGs. like reference numbers will designate like features fromother FIGs. FIG. 2 illustrates an input or RF input 107 to a powerdivider 201 which has a first output or divider output 109 and a secondoutput or divider output 111 (I/O numbered same as FIG. 1). The powerdivider as illustrated is implemented with one or more inductivereactances 203, 209, e.g., lumped element or discrete elementinductances, and one or more capacitive reactances 205, 207, e.g.,lumped element or discrete element capacitances, as well as a resistiveloss or resistor 211. Lumped or discrete element is used herein todistinguish, for example, between structures whose purpose, structure,and properties are for providing a reactance as opposed to structureswith a distributed structure, such as strip line or micro strip linebased transmission lines, which can under some circumstances displayproperties that include or are similar to an inductive or capacitivereactance. As shown a shunt inductance 203 or inductor is coupled fromthe input to a reference node (ground) 204. This inductance will operateto reduce power in any low frequency signals at the input. Two seriescapacitances 205, 207 or capacitors 205, 207 are coupled from the inputto, respectively, the first divider output 109 and the second divideroutput 111. These capacitances will typically be equal valued for a 3 dBsplitter. A series coupled inductance 209 and resistance 211 is coupledbetween the first and second divider outputs and operates to balance thesignal at these outputs. The actual values for the inductors andcapacitors and resistor will vary in accordance with operatingfrequencies and operating impedances. Generally the shunt inductor 203in combination with capacitor 207 forms a high pass structure whichexhibits an impedance transformation between 107 (100 ohms for example)to 111 (50 ohms for example). Similarly, inductor 203 in combinationwith capacitor 205 forms a high pass structure which exhibits animpedance transformation between 107 (100 ohms for example) to 109 (50ohms for example). Resistor 211 in combination with inductor 209 createsa 50 ohm (nominal) odd-mode impedance at nodes 111 and 109. Thecombination of the elements is such that nodes 107, 109, and 111 eachexhibit an impedance of 50 ohms (for example) and the combination ofelements can be further chosen such that an equal or unequal power issplit from 107 to 111 and 107 to 109, respectively. One of ordinaryskill can readily and experimentally determine the appropriate valuesfor a given application. An alternative embodiment for the powersplitter could use transmission lines although it is noted that theseembodiments may not be as useful (e.g., much larger in physical size)over as broad of a bandwidth as the lumped element embodiments.

FIG. 2 also illustrates an embodiment of the fixed phase shifter inaccordance with fixed phase shifter 127 and more specifically two fixed,but opposite direction phase shifters. One is a negative shift 229 suchas a negative forty five degree shift that is coupled to divider output109 and provides an output that goes to adjustable attenuator 115 (seeFIG. 1). This negative shift 229 corresponds to negative shift 129 ofFIG. 1. The negative shift 229 is a lumped element circuit having orimplemented with an inductive reactance 233 coupled from divider output109 to adjustable attenuator 115 and further having an input capacitivereactance 235 coupled from divider output 109 to a reference node(ground) 204 and an output capacitive reactance 237 or capacitor coupledfrom adjustable attenuator 115 input to the reference node 204. Thespecific values for the inductors and capacitors will depend onoperating impedances and signal frequencies but can be experimentallydetermined by practitioners without undue experimentation.

The other fixed shift is a positive shift 231, such as a positive fortyfive degree shift that is coupled to divider output 111 and provides anoutput that goes to adjustable attenuator 121 (see FIG. 1). The positiveshift 231 corresponds to the positive shift 131 of FIG. 1. The positiveshift 231 is a lumped element circuit having an input capacitivereactance 239 coupled from divider output 111 to a common node 240 andan output capacitive reactance 241 or capacitor coupled from the commonnode 240 to adjustable attenuator 121 input. Further included is aninductive reactance 233 coupled from the common node 240 to thereference node (ground) 204. The specific values for the inductors andcapacitors will depend on operating impedances and signal frequenciesbut can be experimentally determined by practitioners without undueexperimentation.

Referring to FIG. 3, a representative diagram of an adjustableattenuator in accordance with one or more embodiments will be discussedand described. FIG. 3 shows a representative embodiment of an adjustableattenuator suitable for use in the FIG. 1 adjustable power splitter.FIG. 3 illustrates an input 301 (analogous to input to adjustableattenuator 115 or 121 in FIG. 1) to a first variable attenuator 303,which provides either 0 db or 2 db of attenuation, where 2 dB isprovided when b2 304 is high or equal to 1. The first variableattenuator is a resistive divider with a switch around the divider (notspecifically shown). The control line b2 opens this switch. The firstvariable attenuator 303 is coupled to a second variable attenuator 305which provides an attenuated signal at output 307 (analogous to input to113, 119 in FIG. 1). The second variable attenuator is shown in moredetail and is arranged and configured to provide 0 dB to 1.5 dB ofattenuation in 0.5 dB steps, i.e., 0 dB, 0.5 dB, 1.0 dB, or 1.5 dB ofattenuation where these steps or attenuations can be referred to asnegative gains (e.g., −0.5 dB gain). Thus the serial combination ofadjustable attenuator 303 and 307 can provide from 0 dB up to 3.5 dB ofattenuation depending on control signal states, i.e., step through 0-1.5dB with attenuator 305 and then bring in 2 dB with attenuator 303 and gothrough or repeat the steps, 0-3.5 dB, with attenuator 305.

Further shown in FIG. 3 is a table 309 of input signals b0, b1, andswitch control signals s1-s4 which result from the input signals b0, b1together with expected attenuation as a function of a particularcombination of s1-s4. By observation s1 is the logical OR inverted (NOR)of b0, b1, i.e., high only when both inputs are low and low otherwise.Similarly s2 is the OR of b0, b1, i.e., high if either input is high.Further s3 is equal to b0 and s4 is the logical AND of b0, b1, i.e.,high only if both inputs are high.

In more detail, the first adjustable attenuator 303 is coupled to acapacitance 311 which will have a near zero impedance for signals ofinterest and this capacitance is coupled to a resistor 313 which is arelatively high value and is used for biasing purposes. Supply noise iscoupled to ground by capacitor 314. Capacitor 311 is further coupled toswitch S1 315, switch S2 317, and resistor 319. When S1 is ON, (s1=1 orhigh and coupled to the transistor gate, as shown, via a control lead orresistor) there will be near zero attenuation as the input signal atcapacitor 311 will be coupled via S1 to the output capacitor 321 andthus output 307 since the output capacitor is near zero impedance forsignals of interest (see also table, line 1). When S1 is OFF and S2 isON (s1=0, s2=1 or high), the input signal at capacitor 311 will becoupled to resistor 323 and from there to the output capacitor 321. Theinput signal will also be coupled through the series combination ofresistor 319 and 324 to the output capacitor 321. Resistors 323 inparallel with the series combination of resistors 319, 324 are chosen toprovide an attenuation of 0.5 dB given the operating frequencies andimpedances (see table, line 2). If, in addition to S2 being ON, switchS3 325 is ON (s3=1 or high), the signal at the node between resistors319, 324 will be coupled via resistor 327 to capacitor 328 and thusground. This will increase the attenuation and resistor 327 is selectedsuch that an additional 0.5 dB or a total of 1.0 dB of attenuation isprovided with this combination of switches (see table, line 3). If inaddition to S2 and S3, switch S4 331 is ON (s4=1 or high) resistor 333will be added in parallel with resistor 327 and the signal will befurther attenuated. Resistor 333 is chosen to add a further 0.5 dB for atotal of 1.5 dB of attenuation to the signal at the output (see table,line 4). Those of ordinary skill given a specific application withoperating frequencies and impedances can determine the appropriatevalues of the resistors by calculation or experimentation.

Referring to FIG. 4, a representative diagram of an adjustable phaseshifter in accordance with one or more embodiments will be discussed anddescribed. The adjustable phase shifter illustrated in FIG. 4 is oneembodiment of the subject matter of co-pending patent application,titled A DELAY LINE PHASE SHIFTER WITH SELECTABLE PHASE SHIFT bySTAUDINGER with the same filing date as the present application andidentified by Ser. No. 13/360,119, which application is herebyincorporated herein by reference.

FIG. 4 illustrates a high level diagram of a phase shifter or delay linephase shifter with selectable phase shift in accordance with one or moreembodiments. In FIG. 4, an adjustable phase shifter 400 with selectableor variable phase shift is shown in a representative manner. The phaseshifter 400 has an input coming from adjustable attenuator 115 or 121 inFIG. 1 or a signal input for input signals, e.g., radio frequency (RF)signals and an output coupled to divider or divider power outputs 117,123 or a signal output for phase shifted versions of the input signal,e.g., phase shifted versions of the RF signals. Between the input 103and output 105 are one or more switchable phase shifting elements orcircuits, including specifically phase shifting elements 401, 411, 421,and possibly additional phase shifting elements or circuits 431 seriallycoupled as shown.

Generally speaking in many embodiments and as will be further discussedand described below, the switches shown are provided with a pair ofsingle throw switches a, b for each phase shifting element 401, 411,421. Each of the phase shifting elements can be designed, arranged andconfigured to provide some predetermined amount of phase shift. If apractitioner needs to cover a certain range of phase shift and needs acertain resolution for the phase shift it can be advantageous to designthe first or one of the phase shifting elements to provide a choicebetween nominally zero or a minimal phase shift and the smallest phaseshift step one needs (i.e., the resolution) with the next or anotherphase shifting element configured to provide minimal or 2× the smalleststep needed. Thus with two phase shifting elements you can provide anear zero, 1×, 2×, and 3× small step in phase shift by activatingdifferent combinations of the a, b switches. Adding another phaseshifting element with a 4× shift, allows 8 states with corresponding 0to 7× the small step and so on. The number of phase shifting elementswill be determined by the required resolution (step size) and the phaserange needed to be covered (number of steps). For example if you want tocover 49 degrees with a resolution of 7 degrees then 8 states, including0 will be required and this can be accomplished with 3 phase shiftingelements etc. etc.

In more detail, switchable phase shifting element or circuit 401 (andthe other similar phase shifting elements) further comprises a firstsignal path coupled between the input through a switch 403 oralternatively with switch 405 closed through phase shifting circuit 407to an output 410. The first signal path, when activated by closing oractivating switch 403 or integrated circuit switch, will be providing anear zero phase shift for a signal coupled through the first signalpath. Further included is a second signal path coupled between the inputand the output 410 via the phase shifting circuit 407 (switch 405closed). The second path is configured for providing a second phaseshift for a signal coupled through the second signal path. Basicallyswitch 403 selects between the first path and the second path or betweenzero and some phase shift. Insertion loss is equalized between the firstpath and the second path by switching in (opening switch 405) a losscircuit, resistor 409, when the first signal path is selected. Theswitches 403, 405, 413, 415, 423, and 425, etc. are controlled by acontrol circuit, e.g., controller 125 or another controller or latch,which can alternatively be viewed as a portion of the phase shifter withselectable phase shift.

In these embodiments or other embodiments, when the switch or integratedcircuit switch 403 is activated (closed or ON) thus selecting the firstsignal path, the resistive loss circuit or resistor 409 is switched in(switch 405 open or OFF) and is configured or value chosen to equalizethe first insertion loss for the first path and the second insertionloss expected when the second signal path is selected (i.e., switch 403is open and 405 is closed).

Various embodiments of the phase shifting circuit 407 as illustrated inFIG. 4 can further comprise a first reactance or inductor series coupledat a common node to a second reactance or inductor and a shunt circuitcoupled from the common node to a reference node, e.g., a groundpotential. The shunt circuit in varying embodiments further comprises athird reactance or capacitor in series with the resistive loss orresistor 409 where the switch or integrated circuit switch 405 is inparallel with the resistor 409. One embodiment uses lumped elementinductors and a metal insulator metal capacitor as well as pseudomorphic high electron mobility transistors (pHEMT) for switches.

When the first switch or first integrated circuit switch 403 is closed,ON, or activated it selects the first signal path (provides a shortcircuit around the second signal path) and when the first switch 403 isopen, OFF, or inactivated it deselects (opens) the first signal path andsignal is routed via the second signal path and reactive phase shiftingor changing circuit 407. When the first switch is closed 403 the secondswitch 405 will be open thereby adding the resistive loss circuit 409 tothe reactive circuit 407. This additional loss when the first signalpath is chosen can be selected, i.e., resistor value chosen, byexperimental processes to equalize the insertion loss when the firstsignal path is selected with the insertion loss when the second signalpath is selected, thereby removing any relationship between phase shiftand insertion loss. Typically the resistive loss circuit or resistorwill be several orders of magnitude larger than the ON resistance of anintegrated circuit switch.

The first switch 403 or integrated circuit switch in series with thefirst signal path and the second switch 405 or integrated circuit switchfor switching in the resistive loss circuit 409 are alternativelyactivated (when 403 is ON or CLOSED, 405 is OFF or OPEN andvice-a-versa). Similarly the phase shifting element or circuit 411 whichcan comprise a third switch S2 a 413 or integrated circuit switch inseries with the third signal path and a fourth switch S2 b 415 orintegrated circuit switch for the switching in a second resistive losscircuit 419, wherein the third and fourth switch or integrated circuitswitch are alternatively activated (when one closed other open). In someembodiments, the first (and second) resistive loss circuit is a resistorin parallel with the second (and fourth) integrated circuit switch andthe first (and second) resistive loss circuit is switched in by openingthe second (and fourth) integrated circuit switch, thereby equalizingthe first and second (and third and forth) insertion loss.

The control circuit is arranged to control first, second, third andfourth switches. As suggested above in some embodiments the controlcircuit is configured to select at least one state from available statesof minimal phase shift, a first phase shift, a second phase shift, and afirst plus second phase shift by activating one or more of the first,thus second, and third, thus fourth, integrated circuit switches. Toselect the states in order (near zero phase shift through first plussecond phase shift), switches 403, 413 are ON for near zero, switches405, 413 are ON for a first shift, switches 403, 415 are ON for a secondphase shift, and switches 413, 415 are ON for a first plus second phaseshift. In the above, it is understood that undesignated or unspecifiedswitches are OFF. As suggested above, each time another switchable phaseshifting element or circuit is added, e.g., 421 with switches 423, 425)the number of possible states can double and the range of phase shiftfor a given step size can therefore double or alternatively for a givenrange the resolution can double, i.e., step size can be cut in half.

The controller 125 or control circuit in addition to possibly selectingtiming for activating switches and decoding inputs can, for manyembodiments, by viewed as a register or buffer for storing switch state(ON or OFF) information with one output coupled to each of the switches.The control circuit can be programmed or loaded via inputs 133. Theseinputs may simply specify a state for the phase shifter which is thendecoded by the control circuit into switch states or the inputs can bethe state for each switch or specify how much phase shift is desiredwith the control circuit then determining an appropriate state. Theinputs can be sent to the control circuit via the serial peripheralinterface (SPI). This is a generally known serial interface as indicatedabove.

Referring to FIG. 5-8 various experimental data showing assortedperformance of one or more embodiments will be discussed and described.FIG. 5-6 show efficiency and linearity as a function of phase forvarious attenuator settings where the data was gathered at a poweroutput of 47 dBm from one amplifier and one set of amplifier transistorsusing an adjustable power splitter. FIG. 5 specifically shows phaseadjustment from zero degrees to approximately 45 degrees on thehorizontal axis 501 and plots efficiency percentage on the vertical axis503 as a function of the phase variation for 8 different attenuatorsettings 505. These 8 settings are represented by 8 line graphs 507which is one graph for each 0.5 dB increment in attenuator setting. Asone example, at approximately 40 degrees the second line from the top,i.e., with 3 dB of attenuation, shows approximately 55% efficiency. FIG.6 shows linearity as a function of phase adjustment or shift. The phaseshift is shown on the horizontal axis 601 with linearity (adjacentchannel power ratio—upper side in dB relative to the carrier) on thevertical graph 603 for 8 different attenuator settings 605. These 8settings are represented by 8 line graphs 607 which is one graph foreach 0.5 dB increment in attenuator setting. As one example, atapproximately 40 degrees the second line from the top, i.e., with 3 dBof attenuation, shows approximately 55 dBc linearity. Generally, the wayto use this data is select the attenuation and phase shift that providesacceptable linearity (55 dBc) and the best efficiency—in this instanceapproximately 55%

FIG. 7-8 show amplifier performance for 20 random combinations oftransistors, where these transistors were selected from non averagelots. The random combinations are each inserted into an amplifierfixture and measurements are taken with output power at 47 dBm. FIG. 7specifically shows adjacent channel power ratio on the low and high sideof the carrier 701 with the measured results shown on the vertical axis703. Measurements are taken for fixed or nominal phase setting 704 andfor an optimized phase setting 705. A typical production specificationor limit 706 is shown. All of the measurements for all of thecombinations under each condition are shown in boxes with fixed phaseconditions for lower and higher side shown in boxes 707 and optimizedphase conditions for lower and higher side shown in boxes 709. Byobservation many of the combinations were failing the production limit706 with a fixed or nominal phase setting while all combinations werebetter than the limits with optimized phase settings. Furthermore, themedian measurement 711 in the fixed phase case was well above the limitand toward one end of the box, whereas the median measurement 713 forthe optimized phase case is well within the production limits and muchcloser to the center of the box. FIG. 8 shows measured % efficiencies onthe vertical axis 801 for the random combinations in a Doherty amplifierusing digital pre distortion (DPD) for fixed or nominal phase setting803 and optimized phase settings 805 with measured efficiencies shownin, respective, boxes 806, 807. By observation % efficiencies haveimproved by 1 to 3% with an average improvement of approximately 2%.

Referring to FIG. 9, a flow chart of exemplary processes included in amethod of adjusting or providing a power split signal or adjusting apower splitter that can be used in conjunction with the FIG. 1 system inaccordance with one or more embodiments will be discussed and described.It will be appreciated that this method uses many of the inventiveconcepts and principles discussed in detail above and thus thisdescription will be somewhat in the nature of a summary with variousdetails generally available in the earlier descriptions. This method canbe implemented in one or more of the structures or apparatus describedearlier or other similarly configured and arranged structures. It willbe appreciated that the method can be performed as many times as desiredor continually performed as needed.

The method of providing a power split signal or adjusting a powersplitter illustrated in FIG. 9 includes splitting 901 an input signalinto first and second signals at first and second divider outputs. Thiscan include using a lumped element circuit including an inductivereactance and a capacitive reactance. This may also necessitateproviding a power divider or splitter with an input and a first andsecond divider output where the power divider is configured to split aninput signal into first and second signals at the first and seconddivider outputs. The providing can include providing a lumped elementcircuit including an inductive reactance and a capacitive reactance.

Also included in the method of FIG. 9 is adjusting 903 a phase shift andattenuation of the first signal to provide a first resultant signal at afirst power output; which can include, e.g., using a first adjustablephase shifter and first adjustable attenuator that are each digitallycontrolled with each having multiple states.

In some embodiments this may include disposing a first adjustable phaseshifter and first adjustable attenuator series coupled to the firstdivider output and arranged and configured to phase shift and attenuatethe first signal and provide a first resultant signal at a first poweroutput. These can each be digitally controlled with each having multiplestates, e.g., 8 states. The adjustable attenuators can have multipleattenuation states with each state having a different amount or valuefor attenuation and the adjustable phase shifters can have multiplephase shift or shifting states with each such state having a differentamount of or value for the corresponding phase shift.

Next shown is adjusting 905 a phase shift and attenuation of the secondsignal to provide a second resultant signal at a second power output;which can include, e.g., using a second adjustable phase shifter andsecond adjustable attenuator that are each digitally controlled witheach having multiple states. This can be accomplished in some instancesby disposing a second adjustable phase shifter and second adjustableattenuator series coupled to the second divider output and arranged andconfigured to phase shift and attenuate the second signal and provide asecond resultant signal at a second power output. Again, these can eachbe digitally controlled with each having multiple states. In someinstances, the adjusting a phase shift and attenuation of the firstsignal further comprises using a first adjustable phase shifter having amultiplicity of phase shifted states, e.g., 8 states, with each suchstate providing a different phase shift and first adjustable attenuatorhaving a multiplicity of attenuation states, e.g., 8 states, with eachattenuation state providing a different attenuation value, wherein theadjusting a phase shift includes shifting a phase of the first signal inaccordance with the phase shift for a selected one of the multiplicityof phase shifted states and the adjusting the attenuation includeschanging a level of the first signal in accordance with the attenuationvalue for a selected one of the multiplicity of attenuation states

In some embodiments, the method includes providing 907 a fixed phaseshift between the first and second resultant signals, which can furthercomprise, e.g., providing a negative forty five degree shift for thefirst resultant signal at the first power output and a positive fortyfive degree phase shift for the second resultant signal at the secondpower output. Again disposing a fixed phase shifter arranged andconfigured to provide a fixed phase shift between signals at the firstand second power output, e.g., to provide a negative forty five degreeshift for the first resultant signal at the first power output and apositive forty five degree phase shift for the second resultant signalat the second power output. In most embodiments, the method includescontrolling 909 the adjustable phase shifters and adjustableattenuators. Controlling can includes providing digital phase controlsignals to the adjustable phase shifters to control the phase shift of asignal coupled through the, respective, adjustable phase shifters andproviding digital attenuator control signals to the adjustableattenuators to control the attenuation of any signal coupled throughthe, respective, adjustable attenuator.

It will be appreciated that the above described functions and adjustablesignal or power splitters may be implemented with one or more integratedcircuits or hybrid structures including lumped or discrete components orelements or transmission lines or combinations or the like. Theprocesses, apparatus, and systems, discussed above, and the inventiveprinciples thereof are intended to and can alleviate yield andperformance issues caused by prior art techniques. Using theseprinciples of independent adjustment of phase or signal level or signalattenuation within a power splitter can quickly resolve performance andproduction yield problems in, e.g., Doherty amplifiers with relativelyminor costs and the like.

This disclosure is intended to explain how to fashion and use variousembodiments in accordance with the invention rather than to limit thetrue, intended, and fair scope and spirit thereof. The foregoingdescription is not intended to be exhaustive or to limit the inventionto the precise form disclosed. Modifications or variations are possiblein light of the above teachings. The embodiment(s) was chosen anddescribed to provide the best illustration of the principles of theinvention and its practical application, and to enable one of ordinaryskill in the art to utilize the invention in various embodiments andwith various modifications as are suited to the particular usecontemplated. All such modifications and variations are within the scopeof the invention as determined by the appended claims, as may be amendedduring the pendency of this application for patent, and all equivalentsthereof, when interpreted in accordance with the breadth to which theyare fairly, legally, and equitably entitled.

What is claimed is:
 1. An adjustable power splitter comprising: a powerdivider including an input and a first and second divider output; afirst adjustable phase shifter and first adjustable attenuator seriescoupled to the first divider output and providing a first power output;and a second adjustable phase shifter and second adjustable attenuatorseries coupled to the second divider output and providing a second poweroutput, the first and second power output coupled to a Doherty poweramplifier.
 2. The adjustable power splitter of claim 1 wherein the firstadjustable phase shifter has a plurality of phase shifted states witheach such state providing a different phase shift.
 3. The adjustablepower splitter of claim 2 wherein the first adjustable phase shifter hasa multiplicity of phase shifted states.
 4. The adjustable power splitterof claim 2 wherein the second adjustable phase shifter has amultiplicity of second phase shifted states with each such second stateproviding a different second phase shift.
 5. The adjustable powersplitter of claim 1 wherein the first adjustable attenuator has aplurality of attenuation states with each attenuation state providing adifferent attenuation value.
 6. The adjustable power splitter of claim 5wherein the first adjustable attenuator has a multiplicity ofattenuation states.
 7. The adjustable power splitter of claim 5 whereinthe second adjustable attenuator has a multiplicity of secondattenuation states with each second attenuation state providing adifferent second attenuation value.
 8. The adjustable power splitter ofclaim 1 wherein the power divider is a lumped element circuit includingan inductive reactance and a capacitive reactance.
 9. An adjustablepower splitter comprising: a power divider including an input and afirst and second divider output; a first adjustable phase shifter andfirst adjustable attenuator series coupled to the first divider outputand providing a first power output; a second adjustable phase shifterand second adjustable attenuator series coupled to the second divideroutput and providing a second power output; and a fixed phase shifterconfigured for adding a fixed phase shift between first and secondsignals, the first and second signals at the first and second poweroutputs.
 10. The adjustable power splitter of claim 9 wherein the fixedphase shift is a negative forty five degree shift for the first signaland a positive forty five degree phase shift for the second signal. 11.The adjustable power splitter of claim 9 wherein the fixed phase shifteris a lumped element circuit having an inductive reactance and acapacitive reactance.
 12. The adjustable power splitter of claim 1further comprising a controller for controlling the adjustable phaseshifters and adjustable attenuators, the controller providing discretecontrol signals for controlling phase shifted values for the first andsecond adjustable phase shifters and for controlling attenuation valuesfor the first and second adjustable attenuators.
 13. An adjustable powersplitter comprising: a power divider including an input and a first andsecond divider output; a first adjustable phase shifter and firstadjustable attenuator series coupled to the first divider output andproviding a first power output; and a second adjustable phase shifterand second adjustable attenuator series coupled to the second divideroutput and providing a second power output; and a Doherty poweramplifier with a main amplifier coupled to the first power output and apeaking amplifier coupled to the second power output.
 14. The adjustablepower splitter including a Doherty amplifier of claim 13 wherein thefirst and second adjustable phase shifters have multiple phase shiftedstates where each phase shifted state provides a different phase shiftand the first and second adjustable attenuators have multipleattenuation states where each attenuation state provides a differenceattenuation value are digitally controlled with each having multiplestates.
 15. The adjustable power splitter including a Doherty amplifierof claim 13 wherein the power splitter is characterized as a radiofrequency power splitter and the Doherty amplifier is furthercharacterized as radio frequency Doherty amplifier.
 16. A method ofproviding a power split signal comprising: splitting an input signalinto first and second signals at a first and a second divider outputs;adjusting a phase shift and attenuation of the first signal to provide afirst resultant signal at a first power output; adjusting a phase shiftand attenuation of the second signal to provide a second resultantsignal at a second power output; and providing a fixed phase shiftbetween the first and second resultant signals.
 17. The method ofproviding a power split signal of claim 16 wherein the splitting aninput signal further comprises using a lumped element circuit includingan inductive reactance and a capacitive reactance.
 18. The method ofproviding a power split signal of claim 16 wherein the adjusting a phaseshift and attenuation of the first signal further comprises using afirst adjustable phase shifter having a multiplicity of phase shiftedstates with each such state providing a different phase shift and firstadjustable attenuator having a multiplicity of attenuation states witheach attenuation state providing a different attenuation value, whereinthe adjusting a phase shift includes shifting a phase of the firstsignal in accordance with the phase shift for a selected one of themultiplicity of phase shifted states and the adjusting the attenuationincludes changing a level of the first signal in accordance with theattenuation value for a selected one of the multiplicity of attenuationstates.
 19. The method of providing a power split signal of claim 16wherein the providing a fixed phase shift between the first and secondresultant signals, further comprises providing a negative forty fivedegree shift for the first resultant signal at the first power outputand a positive forty five degree phase shift for the second resultantsignal at the second power output.
 20. The method of providing a powersplit signal of claim 16 further comprising providing digital phasecontrol signals to the adjustable phase shifters to control the phaseshift of a signal coupled through the, respective, adjustable phaseshifters and providing digital attenuator control signals to theadjustable attenuators to control the attenuation of any signal coupledthrough the, respective, adjustable attenuator.